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MP1591

2A, 32V, 330KHz

Step-Down Converter

The Future of Analog IC Technology

DESCRIPTION

FEATURES

The MP1591 is a high voltage step-down

converter ideal for automotive power adapter

battery chargers. Its wide 6.5V to 32V input

voltage range covers the automotive battery’s

requirements and it achieves 2A continuous

output for quick charge capability.

•

Wide 6.5V to 32V Input Operating Range

34V Absolute Maximum Input

2A Output Current

120mΩ Internal Power MOSFET Switch

Stable with Low ESR Output Ceramic

Capacitors

•

Up to 95% Efficiency

20µA Shutdown Mode

Fixed 330KHz Frequency

Thermal Shutdown

Cycle-by-Cycle Over Current Protection

Output Adjustable From 1.23V to 21V

Under Voltage Lockout

Reference Voltage Output

Available in 8-Pin SOIC Packages

Current mode operation provides fast transient

response and eases loop stabilization. Fault

protection includes cycle-by-cycle current

limiting and thermal shutdown. In shutdown

mode, the converter draws only 20µA of supply

current.

The MP1591 requires a minimum number of

readily available external components to

complete a 2A step-down DC to DC converter

solution.

APPLICATIONS

EVALUATION BOARD REFERENCE

•

Automotive Power Adapters

PDA and Cellular Phone Battery Chargers

Distributed Power Systems

Board Number

Dimensions

EV0020

2.1”X x 1.4”Y x 0.5”Z

Automotive Aftermarket Electronics

“MPS” and “The Future of Analog IC Technology” are Registered Trademarks of

Monolithic Power Systems, Inc.

TYPICAL APPLICATION

C2

10nF

Efficiency vs

INPUT

6.5V to 32V

Load Current

100

V

=5V

OUT

90

80

70

60

50

40

30

20

2

1

V

=3.3V

OUT

IN

BS

OUTPUT

2.5V

2A

7

8

3

EN

SW

OFF ON

MP1591

D1

5

OPEN

NOT USED

REF

GND

FB

COMP

4

6

C4

4.7nF

C3

V

=12V

IN

OPEN

0

0.5

1

1.5

2

LOAD CURRENT (A)

MP1591 Rev. 2.3

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1

MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

PACKAGE REFERENCE

ABSOLUTE MAXIMUM RATINGS ⁽¹⁾

IN Supply Voltage........................–0.3V to +34V

SW Voltage............................. –1V to V_IN+ 0.3V

BS Voltage ....................V_SW– 0.3V to V_SW+ 6V

All Other Pins.................................–0.3V to +6V

Junction Temperature...............................150°C

Lead Temperature....................................260°C

Storage Temperature ..............–65°C to +150°C

Recommended Operating Conditions ⁽²⁾

Input Voltage ................................... 6.5V to 32V

Operating Temperature .............–40°C to +85°C

TOP VIEW

BS

IN

1

2

3

4

8

7

6

5

REF

EN

SW

GND

COMP

FB

EXPOSED PAD

ON BACKSIDE

(SOIC8N ONLY)

CONNECT TO PIN 4

Thermal Resistance ⁽³⁾

θ_JA

θ_JC

SOIC8 (w/ Exposed Pad) .......50...... 10... °C/W

SOIC8.....................................90...... 45... °C/W

Part Number*

Package

Temperature

–40°C to +85°C

MP1591DN

MP1591DS

SOIC8E

SOIC8

Notes:

1) Exceeding these ratings may damage the device.

2) The device is not guaranteed to function outside of its

operating conditions.

For Tape & Reel, add suffix –Z (eg. MP1591DN–Z)

For RoHS Compliant Packaging, add suffix –LF

(eg. MP1591DN–LF–Z)

*

3) Measured on approximately 1” square of 1 oz copper.

ELECTRICAL CHARACTERISTICS

V_IN= 12V, T_A= +25°C, unless otherwise noted.

Parameter

Symbol Condition

Min

Typ

20

Max

35

Units

µA

Shutdown Supply Current

Supply Current

V_EN= 0V

V_EN= 5V, V_FB= 1.4V

6.5V ≤ V_IN≤ 32V, V_COMP< 2V

1.0

1.2

mA

V

Feedback Voltage

1.202 1.230 1.258

400

Error Amplifier Voltage Gain

Error Amplifier Transconductance

High-Side Switch On Resistance ⁽⁴⁾

Low-Side Switch On Resistance ⁽⁴⁾

High-Side Switch Leakage Current

Current Limit ⁽⁵⁾

V/V

µA/V

mꢀ

ꢀ

500

700

120

8.5

0

1100

∆I_C= ±10µA

V_EN= 0V, V_SW= 0V

10

µA

2.5

3.6

4.9

A

Current Sense to COMP

Transconductance

3.5

A/V

Oscillation Frequency

280

330

35

380

KHz

%

Short Circuit Oscillation Frequency

Maximum Duty Cycle ⁽⁴⁾

Minimum Duty Cycle ⁽⁴⁾

V_FB= 0V

V_FB= 1.0V

V_FB= 1.5V

90

0

%

EN Shutdown Threshold Voltage

Enable Pull-Up Current

0.8

2.4

1.2

1.8

2.6

250

1.6

V

V_EN= 0V

µA

V

EN UVLO Threshold

V_ENRising

2.8

EN UVLO Threshold Hysteresis

mV

MP1591 Rev. 2.3

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2

MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

ELECTRICAL CHARACTERISTICS (continued)

V_IN= 12V, T_A= +25°C, unless otherwise noted.

Parameter

Symbol Condition

Min

Typ

160

5.0

100

30

Max

Units

°C

Thermal Shutdown ⁽⁴⁾

REF Voltage

I_REF= 0

V

REF Load Regulation ⁽⁴⁾

REF Line Regulation ⁽⁴⁾

Notes:

∆I_REF= 0 to 1mA

I_REF= 100µA, V_IN= 6.5 to 32V

mV

4) These parameters are guaranteed by design, not production tested.

5) Equivalent output current = 1.5A ≥ 50% Duty Cycle

2.0A ≤ 50% Duty Cycle

Assumes ripple current = 30% of load current.

Slope compensation changes current limit.

PIN FUNCTIONS

Pin # Name Description

1

2

BS

IN

High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET

switch. Connect a 10nF or greater capacitor from SW to BS to power the high-side switch.

Power Input. IN supplies the power to the IC, as well as the step-down converter switches.

Drive IN with a 6.5V to 32V power source. Bypass IN to GND with a suitably large capacitor to

eliminate noise on the input to the IC. See Input Capacitor.

3

SW

Power Switching Output. SW is the switching node that supplies power to the output. Connect

the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS

to power the high-side switch.

4

5

GND Ground. For the MP1591DN, connect the Exposed Pad to pin 4.

FB

Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive

voltage divider from the output voltage. The feedback threshold is 1.230V. See Setting the

Output Voltage.

6

COMP Compensation Node. COMP is used to compensate the regulation control loop. Connect a

series RC network from COMP to GND to compensate the regulation control loop. In some

cases, an additional capacitor from COMP to GND is required. See Compensation.

7

8

EN

Enable/UVLO. A voltage greater than 2.8V enables operation. For complete low current

shutdown the EN pin voltage needs to be less than 800mV.

REF Reference Output. REF is the 5V reference voltage output. It can supply up to 1mA to external

circuitry. If used, bypass REF to GND with 10nF or greater capacitor. Leave REF unconnected

if not used.

MP1591 Rev. 2.3

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3

MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

OPERATION

The MP1591 is a current mode step-down

regulator. It regulates input voltages from 6.5V

to 32V down to an output voltage as low as

1.230V and is able to supply up to 2A of load

current.

The voltage at COMP is compared to the switch

current measured internally to control the output

voltage. The converter uses an internal

N-Channel MOSFET switch to step-down the

input voltage to the regulated output voltage.

Since the MOSFET requires a gate voltage

greater than the input voltage, a boost capacitor

connected between SW and BS drives the gate.

The capacitor is internally charged while SW is

low. An internal 10ꢀ switch from SW to GND is

used to insure that SW is pulled to GND when

the switch is off to fully charge the BS capacitor

The MP1591 uses current-mode control to

regulate the output voltage. The output voltage

is measured at FB through a resistive voltage

divider and amplified through the internal error

amplifier. The output current of the

transconductance error amplifier is presented at

COMP where a network compensates the

regulation control system.

2

8

IN

CURRENT

SENSE

AMPLIFIER

5V

INTERNAL

REF

REGULATORS

+

--

OSCILLATOR

SLOPE

COMP

1

3

BS

35/330KHz

CLK

M1

M2

+

--

+

S

R

Q

SW

CURRENT

COMPARATOR

SHUTDOWN

COMPARATOR

--

1.2V

7

EN

LOCKOUT

COMPARATOR

--

+

1.8V

2.60V/

2.35V

4

GND

THERMAL

PROTECTION

ERROR

AMPLIFIER

+

--

+

0.7V 1.230V

--

FREQUENCY

FOLDBACK

COMPARATOR

5

6

FB

COMP

Figure 1—Functional Block Diagram

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

APPLICATION INFORMATION

The inductance value can be calculated by the

equation:

COMPONENT SELECTION

Setting the Output Voltage

The output voltage is set using a resistive

voltage divider from the output voltage to FB.

The voltage divider divides the output voltage

down by the ratio:

(V_IN− V_OUT

)

L1 = V_OUT

×

(V_IN× f × ∆I)

Where V_INis the input voltage, f is the switching

frequency and ꢁI is the peak-to-peak inductor

ripple current.

R2

V_FB= V_OUT

×

(R1+ R2)

Table 1 lists a number of suitable inductors

from various manufacturers.

Where V_FBis the feedback voltage and V_OUTis

the output voltage.

Table 1—Inductor Selection Guide

Thus the output voltage is:

Package

Dimensions

(R1+ R2)

V_OUT= 1.230 ×

(mm)

Vendor/

Model

Core

Type

Core

Material

R2

W

L

H

A typical value for R2 can be as high as 100kꢀ,

but 10kꢀ is recommended. Using that value, R1

is determined by:

Sumida

CR75

Open

Ferrite

7.0 7.8 5.5

7.3 8.0 5.2

5.5 5.7 5.5

6.7 6.7 3.0

CDH74

R1 ≅ 8.18 × (V_OUT− 1.230)

CDRH5D28 Shielded Ferrite

CDRH6D28 Shielded Ferrite

For example, for a 3.3V output voltage, R2 is

10kꢀ, and R1 is 17kꢀ.

Inductor (L1)

CDRH104R Shielded Ferrite 10.1 10.0 3.0

The inductor is required to supply constant

current to the output load while being driven by

the switched input voltage. A larger value

inductor results in less ripple current that results

in lower output ripple voltage. However, the

larger value inductor has a larger physical size,

higher series resistance, and/or lower

saturation current. Choose an inductor that

does not saturate under the worst-case load

conditions. A good rule to use for determining

the inductance is to allow the peak-to-peak

ripple current in the inductor to be

approximately 30% of the maximum load

current that the IC can provide. Also, make sure

that the peak inductor current (the load current

plus half the peak-to-peak inductor ripple

current) is below the 2.3A minimum current

limit.

Toko

D53LC

Type A

Shielded Ferrite

5.0 5.0 3.0

7.6 7.6 5.1

D75C

D104C

Shielded Ferrite 10.0 10.0 4.3

D10FL

Open

Ferrite

9.7 1.5 4.0

Coilcraft

DO3308

DO3316

Open

Ferrite

9.4 13.0 3.0

9.4 13.0 5.1

Input Capacitor (C1)

The input current to the step-down converter is

discontinuous, and so a capacitor is required to

supply the AC current to the step-down

converter while maintaining the DC input

voltage. A low ESR capacitor is required to

keep the noise at the IC to a minimum. Ceramic

capacitors are preferred, but tantalum or low

ESR electrolytic capacitors may also suffice.

MP1591 Rev. 2.3

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5

MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

The input capacitor value should be greater

than 10µF. The capacitor can be electrolytic,

tantalum or ceramic. However, since it absorbs

the input switching current it requires an

adequate ripple current rating. Its RMS current

rating should be greater than approximately 1/2

of the DC load current.

Output Rectifier Diode (D1)

The output rectifier diode supplies the current to

the inductor when the high-side switch is off. To

reduce losses due to the diode forward voltage

and recovery times, use a Schottky rectifier.

Table 2 provides some recommended Schottky

rectifiers based on the maximum input voltage

and current rating.

For insuring stable operation C1 should be

placed as close to the IC as possible.

Alternately, a smaller high quality ceramic

0.1µF capacitor may be placed closer to the IC

and a larger capacitor placed farther away. If

using this technique, it is recommended that the

larger capacitor be a tantalum or electrolytic

type. All ceramic capacitors should be placed

close to the MP1591.

Table 2—Diode Selection Guide

2A Load Current

3A Load Current

V_IN

(Max)

Part

Vendor

Number

30BQ15

B220

15V

20V

4

1

B320

SK33

1

1, 6

3

SK23

6

SR22

6

SS32

20BQ030

B230

4

B330

1

Output Capacitor (C5)

1

B340L

MBRD330

SK33

1

The output capacitor is required to maintain the

DC output voltage. Low ESR capacitors are

preferred to keep the output voltage ripple low.

The characteristics of the output capacitor also

affect the stability of the regulation control

system. Ceramic, tantalum or low ESR

electrolytic capacitors are recommended. In the

case of ceramic capacitors, the impedance at

the switching frequency is dominated by the

capacitance, and so the output voltage ripple is

mostly independent of the ESR. The output

voltage ripple is estimated to be:

30V

34V

SK23

6

4, 5

1, 6

2, 3

1

SR23

3, 6

2, 3

4

SS23

SS33

21DQ04

MBRS240L

SK24

B340L

MBRS340

SK34

5

4

6

1, 6

2, 3

SS24

2, 3

SS34

Table 3 lists manufacturer’s websites.

Table 3—Schottky Diode Manufacturers

#

1

2

3

4

5

6

Vendor

Web Site

Diodes, Inc.

www.diodes.com

2

⎛

⎜

⎝

⎞

⎟

⎠

f_LC

V_RIPPLE≅ 1.4 × V_IN

×

Fairchild Semiconductor www.fairchildsemi.com

General Semiconductor www.gensemi.com

f_SW

Where V_RIPPLEis the output ripple voltage, f_LCis

the resonant frequency of the LC filter, f_SWis the

switching frequency.

International Rectifier

On Semiconductor

Pan Jit International

www.irf.com

www.onsemi.com

www.panjit.com.tw

In the case of tantalum or low-ESR electrolytic

capacitors, the ESR dominates the impedance

at the switching frequency, and so the output

ripple is calculated as:

Choose a rectifier whose maximum reverse

voltage rating is greater than the maximum

input voltage, and whose current rating is

greater than the maximum load current.

V_RIPPLE≅ ∆I× R_ESR

Where V_RIPPLEis the output voltage ripple and

R_ESRis the equivalent series resistance of the

output capacitors.

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

Compensation

The system crossover frequency f_C,(the

frequency where the loop gain drops to 1, or

0dB) is important. A good rule of thumb is to set

the crossover frequency to approximately one

tenth of the switching frequency. In this case,

the switching frequency is 330KHz, so use a

crossover frequency of 33KHz. Lower

crossover frequencies result in slower response

and worse transient load recovery. Higher

crossover frequencies can result in instability.

The system stability is controlled through the

COMP pin. COMP is the output of the internal

transconductance error amplifier. A series

capacitor-resistor combination sets a pole-zero

combination to control the characteristics of the

control system. The DC loop gain is:

V_REF

A_VDC

=

× A_VEA× G_CS× R_LOAD

V_OUT

Where V_REFis the feedback threshold voltage,

1.230V, A_VEAis the transconductance error

amplifier voltage gain, 400 V/V, and G_CSis the

current sense gain (roughly the output current

divided by the voltage at COMP), 3.5 A/V.

Choosing the Compensation Components

The values of the compensation components

given in Table 4 yield a stable control loop for

the output voltage and given capacitor.

Table 4—Compensation Values for Typical

Output Voltage/Capacitor Combinations

The system has 2 poles of importance; one is

due to the compensation capacitor (C4) and the

other is due to the output capacitor (C5). These

are:

V_OUT

2.5V

3.3V

5V

C5

R3

C3

C4

22µF Ceramic

47µF SP-Cap

3.9kꢀ

5.1kꢀ

7.5kꢀ

18kꢀ

8.2kꢀ

10kꢀ

16kꢀ

36kꢀ

None

4.7nF

3.9nF

2.7nF

1.2nF

2.2nF

1.5nF

1nF

G_MEA

f_P1

=

(2π × A_VEA× C4)

12V

2.5V

3.3V

5V

Where f_P1is the first pole, and G_MEAis the error

amplifier transconductance (770µS) and

1

f_P2

=

(2π × R_LOAD× C5)

12V

The system has one zero of importance due to

the compensation capacitor (C4) and the

compensation resistor (R3) which is

560µF/6.3V, AL

30mꢀ ESR

2.5V

3.3V

5V

100kꢀ

120kꢀ

150kꢀ

180kꢀ

150pF

120pF

82pF

1nF

560µF/6.3V, AL

30mꢀ ESR

1

f_Z1

=

470µF/10V, AL

30mꢀ ESR

(2π × R3 × C4)

220µF/25V, AL

30mꢀ ESR

If large value capacitors with relatively high

equivalent-series-resistance (ESR) are used,

the zero due to the capacitance and ESR of the

output capacitor can be compensated by a third

pole set by R3 and C3

12V

33pF

Note: “AL” = Electrolytic

1

f_P3

=

(2π × R3 × C3)

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

To optimize the compensation components that

are not listed in Table 4, use the following

procedure.

Example:

V_OUT= 5V, C5 = 22µF Ceramic (ESR = 10mꢀ)

R3 ≈ 6.88x10⁷(22x10^-6) (5) = 7568ꢀ

Use the nearest standard value of 7.5kꢀ.

C4 > 1.93x10^-5/ 7.5K = 2.57nF

Use standard value of 2.7nF.

Choose the compensation resistor to set the

desired crossover frequency. Determine the

value by the following equation:

2π × C5 × V_OUT× f_C

R3 =

G_EA× G_CS× V_REF

8π x C5 x R_ESRx f_C= 0.22, which is less than 1.

Therefore, no second compensation capacitor

(C3) is required.

Putting in the know constants and setting the

crossover frequency to the desired 33KHz:

R3 ≅ 6.88 ×10⁷× C5 × V_OUT

External Bootstrap Diode

It is recommended that an external bootstrap

diode be added when the system has a 5V

fixed input or the power supply generates a 5V

output. This helps improve the efficiency of the

regulator. The bootstrap diode can be a low

cost one such as IN4148 or BAT54.

Choose the compensation capacitor to set the

zero below one fourth of the crossover

frequency. Determine the value by the following

equation:

2

1.93 ×10⁻⁵

C4 >

≈

5V

π × R3 × f_C

R3

Determine if the second compensation

capacitor, C3, is required. It is required if the

ESR zero of the output capacitor occurs at less

than four times the crossover frequency, or

1

BS

10nF

MP1591

3

SW

8π × C5 × R_ESR× f_C≥ 1

Figure 2—External Bootstrap Diode

If this is the case, then add the second

compensation resistor. Determine the value by

the equation:

This diode is also recommended for high duty

V_OUT

cycle operation (when

>65%) and high

V_IN

C5 × R_ESR(MAX)

C3 =

output voltage (V_OUT>12V) applications.

R3

Where R_ESR(MAX)is the maximum ESR of the

output capacitor.

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

TYPICAL APPLICATION CIRCUITS

C2

10nF

INPUT

6.5V to 32V

2

1

IN

BS

OUTPUT

2.5V

2A

7

3

EN

SW

OFF ON

MP1591

D1

8

5

OPEN

REF

FB

NOT USED

GND

COMP

4

6

C4

4.7nF

C3

OPEN

Figure 3—MP1591 with Murata 22µF / 10V Ceramic Output Capacitor

C2

10nF

INPUT

6.5V to 32V

2

1

IN

BS

OUTPUT

2.5V

2A

7

8

3

5

EN

SW

OFF ON

MP1591

D1

OPEN

NOT USED

REF

GND

FB

COMP

4

6

C4

2.2nF

C3

OPEN

Figure 4—MP1591 with Panasonic 47µF / 6.3V Special Polymer Output Capacitor

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

PACKAGE INFORMATION

SOIC8

0.189(4.80)

0.197(5.00)

0.050(1.27)

0.024(0.61)

0.063(1.60)

8

5

0.150(3.80)

0.157(4.00)

0.228(5.80)

0.244(6.20)

0.213(5.40)

PIN 1 ID

1

4

TOP VIEW

RECOMMENDED LAND PATTERN

0.053(1.35)

0.069(1.75)

SEATING PLANE

0.004(0.10)

0.010(0.25)

0.0075(0.19)

0.0098(0.25)

0.013(0.33)

0.020(0.51)

SEE DETAIL "A"

0.050(1.27)

BSC

SIDE VIEW

FRONT VIEW

0.010(0.25)

0.020(0.50)

x 45^o

NOTE:

1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN

BRACKET IS IN MILLIMETERS.

GAUGE PLANE

0.010(0.25) BSC

2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,

PROTRUSIONS OR GATE BURRS.

3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH

OR PROTRUSIONS.

4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING)

SHALL BE 0.004" INCHES MAX.

0.016(0.41)

0.050(1.27)

0^o-8^o

5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION AA.

6) DRAWING IS NOT TO SCALE.

DETAIL "A"

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MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER

SOIC8E (WITH EXPOSED PAD)

0.189(4.80)

0.197(5.00)

0.124(3.15)

0.136(3.45)

8

5

0.150(3.80)

0.157(4.00)

0.228(5.80)

0.244(6.20)

0.089(2.26)

0.101(2.56)

PIN 1 ID

1

4

TOP VIEW

BOTTOM VIEW

SEE DETAIL "A"

0.051(1.30)

0.067(1.70)

SEATING PLANE

0.000(0.00)

0.006(0.15)

0.0075(0.19)

0.0098(0.25)

0.013(0.33)

0.020(0.51)

SIDE VIEW

0.050(1.27)

BSC

FRONT VIEW

0.010(0.25)

0.020(0.50)

x 45^o

GAUGE PLANE

0.010(0.25) BSC

0.050(1.27)

0.024(0.61)

0.063(1.60)

0.016(0.41)

0.050(1.27)

0^o-8^o

DETAIL "A"

0.103(2.62)

0.213(5.40)

NOTE:

1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN

BRACKET IS IN MILLIMETERS.

2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,

PROTRUSIONS OR GATE BURRS.

3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH

OR PROTRUSIONS.

0.138(3.51)

4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING)

SHALL BE 0.004" INCHES MAX.

5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA.

6) DRAWING IS NOT TO SCALE.

RECOMMENDED LAND PATTERN

NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third

party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not

assume any legal responsibility for any said applications.

MP1591 Rev. 2.3

9/27/2006

www.MonolithicPower.com

MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.

11

型号:	B340HA
是否Rohs认证：	符合
生命周期：	Active
包装说明：	PLASTIC, SMA, 2 PIN
针数：	2
Reach Compliance Code：	compliant
ECCN代码：	EAR99
HTS代码：	8541.10.00.80
风险等级：	5.62
其他特性：	FREE WHEELING DIODE
应用：	GENERAL PURPOSE
配置：	SINGLE
二极管元件材料：	SILICON
二极管类型：	RECTIFIER DIODE
JESD-30 代码：	R-PDSO-C2
最大非重复峰值正向电流：	80 A
元件数量：	1
相数：	1
端子数量：	2
最高工作温度：	150 °C
最低工作温度：	-55 °C
最大输出电流：	3 A
封装主体材料：	PLASTIC/EPOXY
封装形状：	RECTANGULAR
封装形式：	SMALL OUTLINE
峰值回流温度（摄氏度）：	NOT SPECIFIED
认证状态：	Not Qualified
最大重复峰值反向电压：	40 V
表面贴装：	YES
技术：	SCHOTTKY
端子形式：	C BEND
端子位置：	DUAL
处于峰值回流温度下的最长时间：	NOT SPECIFIED
Base Number Matches：	1

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